Data transmission method and apparatus

ABSTRACT

Embodiments of the present invention provide a data transmission method and apparatus, and the method includes: modulating to-be-sent information bits according to a lower order constellation diagram, and generating 4m lower order modulation symbols; multiplying a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m to-be-sent higher order modulation symbols corresponding to a higher order constellation diagram; and respectively and correspondingly sending the 4m to-be-sent higher order modulation symbols on different carriers of two antennas. The to-be-sent higher order modulation symbols include some or all to-be-sent information bits. Therefore, the same signal can be simultaneously sent on different carriers of multiple antennas, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No. 16/546,159, filed on Aug. 20, 2019, which is a continuation of U.S. patent application Ser. No. 15/975,720, filed on May 9, 2018, now U.S. Pat. No. 10,419,262, which is a continuation of International Application No. PCT/CN2016/104305, filed on Nov. 2, 2016, which claims priority to Chinese Patent Application No. 201510780892.6, filed on Nov. 13, 2015. The disclosures of the aforementioned applications are hereby incorporated by reference in their entireties.

TECHNICAL FIELD

Embodiments of the present invention relate to the communications technologies, and in particular, to a data transmission method and apparatus.

BACKGROUND

Dual carrier modulation (DCM) is a technology that improves transceiving performance by using frequency diversity.

Frequency diversity means that a transmit end simultaneously transmits a signal by using two transmit frequencies with a relatively large interval, and a receive end simultaneously receives two radio-frequency signals and then combines them. Due to different operating frequencies, correlation between electromagnetic waves is extremely slim, and fading probabilities of all electromagnetic waves are different. Therefore, specially, the frequency diversity effectively resists frequency selective fading, and can improve the transceiving performance. For example, it is assumed that signals to be sent are s₁ and s₂, signals x₁ and x₂ are generated after s₁ and s₂ are combined, and x₁=α₁s₁+β₁s₂ and x₂=α₂s₁+β₂s₂. x₁ and x₂ are simultaneously sent on different frequencies (carriers), and the receive end simultaneously receives the two radio-frequency signals and then combines them, so as to implement the frequency diversity, thereby improving the transceiving performance.

However, with rapid development of wireless communications technologies, people's requirement for improving the transceiving performance is further increased, and transceiving performance of a data transmission method in the prior art cannot meet people's requirement.

SUMMARY

Embodiments of the present invention provide a data transmission method and apparatus, so as to improve transceiving performance of data transmission.

According to a first aspect, an embodiment of the present invention provides a data transmission method, including:

modulating information bits to be sent according to a lower order constellation diagram, and generating 4m lower order modulation symbols, where m is an integer greater than or equal to 1;

separately multiplying a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m higher order modulation symbols corresponding to a higher order constellation diagram; and

sending the 4m higher order modulation symbols on different carriers of two antennas respectively.

In one embodiment, the 4m higher order modulation symbols are classified into four types. A 4(i−1)+1^(th) higher order modulation symbol is a first higher order modulation symbol; a 4(i−1)+2^(th) higher order modulation symbol is a second higher order modulation symbol; a 4(i−1)+3^(th) higher order modulation symbol is a third higher order modulation symbol; and a 4(i−1)+4^(th) higher order modulation symbol is a fourth higher order modulation symbol, where 1≤i≤l, and i is an integer.

The sending the 4m to-be-sent higher order modulation symbols on different carriers of two antennas includes:

sending the first higher order modulation symbol on a first subcarrier of a first transmit antenna; sending the second higher order modulation symbol on a first subcarrier of a second transmit antenna; sending the third higher order modulation symbol on a second subcarrier of the first transmit antenna; and sending the fourth higher order modulation symbol on a second subcarrier of the second transmit antenna.

In one embodiment, the separately multiplying a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m to-be-sent higher order modulation symbols corresponding to a higher order constellation diagram includes:

multiplying a precoding matrix

$Q = {\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four quadrature phase shift keying QPSK symbols, to obtain four 256QAM modulation symbols that are corresponding to a 256 quadrature amplitude modulation QAM constellation diagram and [x₀ x₁ x₂ x₃]^(T) respectively, where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, x₃ is the fourth higher order modulation symbol, and [ ]^(T) represents transpose.

In one embodiment, the separately multiplying a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m to-be-sent higher order modulation symbols corresponding to a higher order constellation diagram includes:

multiplying a precoding matrix

$Q = {\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\pi}} \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four QPSK symbols, to obtain four 128QAM modulation symbols that are corresponding to a 128QAM constellation diagram and [x₀ x₁ x₂ x₃]^(T) respectively, where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, x₃ is the fourth higher order modulation symbol, and [ ]^(T) represents transpose.

In one embodiment, the separately multiplying a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m to-be-sent higher order modulation symbols corresponding to a higher order constellation diagram includes:

multiplying a precoding matrix

$Q = {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four BPSK symbols, to obtain four to-be-sent modulation symbols that are corresponding to a QPSK constellation diagram and [x₀ x₁ x₂ x₃]^(T) respectively, where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, and x₃ is the fourth higher order modulation symbol.

According to a second aspect, an embodiment of the present invention provides a data transmission method, including:

receiving, by two receive antennas, signals on two carriers, where the two receive antennas are respectively a first receive antenna and a second receive antenna, the two carriers are respectively a first subcarrier and a second subcarrier, a signal received by the first receive antenna on the first subcarrier is r₁₁, a signal received by the second receive antenna on the first subcarrier is r₂₁, a signal received by the first receive antenna on the second subcarrier is r₁₂, and a signal received by the second receive antenna on the second subcarrier is r₂₂;

obtaining 4m estimated values of lower order modulation symbols after channel equalization is performed on [r₁₁ r₂₁ r₁₂ r₂₂]^(T), where m is an integer greater than or equal to 1; and

demodulating the 4m estimated values of lower order modulation symbols according to a corresponding lower order constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

In one embodiment, the lower order modulation symbol is a quadrature phase shift keying QPSK modulation symbol or a binary phase shift keying BPSK modulation symbol.

According to a third aspect, an embodiment of the present invention provides a data transmission method, including:

performing channel equalization on signals that are received by two antennas on a first subcarrier, to obtain 2m estimated values of first higher order modulation symbols, where m is an integer greater than or equal to 1;

performing channel equalization on signals that are received by the two antennas on a second subcarrier, to obtain 2m estimated values of second higher order modulation symbols;

demodulating the 2m estimated values of first higher order modulation symbols in a mapping manner of a higher order constellation diagram, to obtain a first estimated value of information bits sent by a transmit end;

demodulating the 2m estimated values of second higher order modulation symbols in the mapping manner of the higher order constellation diagram, to obtain a second estimated value of the information bits sent by the transmit end; and

combining the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end, to obtain an estimated value of the information bits sent by the transmit end.

In one embodiment, the higher order modulation symbol is a 256 quadrature amplitude modulation QAM modulation symbol or a quadrature phase shift keying QPSK modulation symbol.

According to a fourth aspect, an embodiment of the present invention provides a data transmission apparatus, including:

a modulation module, configured to modulate to-be-sent information bits according to a lower order constellation diagram, and generate 4m lower order modulation symbols, where m is an integer greater than or equal to 1;

a processing module, configured to separately multiply a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m higher order modulation symbols corresponding to a higher order constellation diagram; and

a sending module, configured to respectively and correspondingly send the 4m higher order modulation symbols on different carriers of two antennas.

In one embodiment, the 4m higher order modulation symbols are classified into four types, a 4(i−1)+1^(th) higher order modulation symbol is a first higher order modulation symbol, a 4(i−1)+2^(th) higher order modulation symbol is a second higher order modulation symbol, a 4(i−1)+3^(th) higher order modulation symbol is a third higher order modulation symbol, and a 4(i−1)+4^(th) higher order modulation symbol is a fourth higher order modulation symbol, where 1≤i≤l, and i is an integer; and

the sending module is configured to: send the first higher order modulation symbol on a first subcarrier of a first transmit antenna; send the second higher order modulation symbol on a first subcarrier of a second transmit antenna; send the third higher order modulation symbol on a second subcarrier of the first transmit antenna; and send the fourth higher order modulation symbol on a second subcarrier of the second transmit antenna.

In one embodiment, the processing module is configured to:

multiply a precoding matrix

$Q = {\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four quadrature phase shift keying QPSK symbols, to obtain four 256QAM modulation symbols that are corresponding to a 256 quadrature amplitude modulation QAM constellation diagram and that are respectively [x₀ x₁ x₂ x₃]^(T), where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, x₃ is the fourth higher order modulation symbol, and [ ]^(T) represents transpose.

In one embodiment, the processing module is configured to:

multiply a precoding matrix

$Q = {\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\pi}} \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four QPSK symbols, to obtain four 128QAM modulation symbols that are corresponding to a 128QAM constellation diagram and that are respectively [x₀ x₁ x₂ x₃]^(T), where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, x₃ is the fourth higher order modulation symbol, and [ ]^(T) represents transpose.

In one embodiment, the processing module is configured to:

multiply a precoding matrix

$Q = {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four BPSK symbols, to obtain four modulation symbols that are corresponding to a QPSK constellation diagram and that are respectively [x₀ x₁ x₂ x₃]^(T), where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, and x₃ is the fourth higher order modulation symbol.

According to a fifth aspect, an embodiment of the present invention provides a data transmission apparatus, including:

a receiving module, configured to receive signals on two carriers, where the receiving module is deployed on a first receive antenna and a second receive antenna, the two carriers are respectively a first subcarrier and a second subcarrier, and a signal received by the first receive antenna on the first subcarrier is r₁₁, a signal received by the second receive antenna on the first subcarrier is r₂₁, a signal received by the first receive antenna on the second subcarrier is r₁₂, and a signal received by the second receive antenna on the second subcarrier is r₂₂;

a channel equalization module, configured to obtain 4m estimated values of lower order modulation symbols after channel equalization is performed on [r₁₁ r₂₁ r₁₂ r₂₂]^(T), where m is an integer greater than or equal to 1; and

a demodulation module, configured to demodulate the 4m estimated values of lower order modulation symbols according to a corresponding lower order constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

In one embodiment, the lower order modulation symbol is a quadrature phase shift keying QPSK modulation symbol or a binary phase shift keying BPSK modulation symbol.

According to a sixth aspect, an embodiment of the present invention provides a data transmission apparatus, including:

a channel equalization module, configured to perform channel equalization on signals that are received by two antennas on a first subcarrier, to obtain 2m estimated values of first higher order modulation symbols, where m is an integer greater than or equal to 1, where

the channel equalization module is further configured to perform channel equalization on signals that are received by the two antennas on a second subcarrier, to obtain 2m estimated values of second higher order modulation symbols;

a demodulation module, configured to demodulate the 2m estimated values of first higher order modulation symbols in a mapping manner of a higher order constellation diagram, to obtain a first estimated value of information bits sent by a transmit end, where

the demodulation module is further configured to demodulate the 2m estimated values of second higher order modulation symbols in the mapping manner of the higher order constellation diagram, to obtain a second estimated value of the information bits sent by the transmit end; and

a processing module, configured to combine the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end, to obtain an estimated value of the information bits sent by the transmit end.

In one embodiment, the higher order modulation symbol is a 256 quadrature amplitude modulation QAM modulation symbol or a quadrature phase shift keying QP SK modulation symbol.

Embodiments of the present invention provide a data transmission method and apparatus, the information bits are modulated according to the lower order constellation diagram, and 4m lower order modulation symbols are generated; the precoding matrix Q is multiplied by the column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain the 4m higher order modulation symbols corresponding to the higher order constellation diagram; and the 4m higher order modulation symbols are respectively and correspondingly sent on different carriers of the two antennas. The higher order modulation symbols include some or all information bits. Therefore, the same signal can be simultaneously sent on different carriers of multiple antennas, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

BRIEF DESCRIPTION OF DRAWINGS

To describe the technical solutions in the embodiments of the present invention more clearly, the following briefly describes the accompanying drawings required for describing the embodiments. Apparently, the accompanying drawings in the following description show merely some embodiments of the present invention, and persons of ordinary skill in the art may still derive other drawings from these accompanying drawings without creative efforts.

FIG. 1 is a schematic diagram of an application scenario according to one embodiment of the present invention;

FIG. 2 is a schematic flowchart of Embodiment 1 of a data transmission method according to one embodiment of the present invention;

FIG. 3 is a schematic flowchart of Embodiment 2 of a data transmission method according to one embodiment of the present invention;

FIG. 4 is a schematic flowchart of Embodiment 3 of a data transmission method according to one embodiment of the present invention;

FIG. 5 is a schematic flowchart of Embodiment 4 of a data transmission method according to one embodiment of the present invention;

FIG. 6 is a BPSK constellation diagram according to one embodiment of the present invention;

FIG. 7 is a QPSK constellation diagram according to one embodiment of the present invention;

FIG. 8 is a schematic flowchart of Embodiment 5 of a data transmission method according to one embodiment of the present invention;

FIG. 9 is a schematic flowchart of Embodiment 6 of a data transmission method according to one embodiment of the present invention;

FIG. 10 is a schematic flowchart of Embodiment 7 of a data transmission method according to one embodiment of the present invention;

FIG. 11 is a 256QAM constellation diagram according to one embodiment of the present invention;

FIG. 12 is a schematic flowchart of Embodiment 8 of a data transmission method according to one embodiment of the present invention;

FIG. 13 is a schematic flowchart of Embodiment 9 of a data transmission method according to one embodiment of the present invention;

FIG. 14 is a schematic flowchart of Embodiment 10 of a data transmission method according to one embodiment of the present invention;

FIG. 15 is a 128QAM constellation diagram according to one embodiment of the present invention;

FIG. 16 is a schematic flowchart of Embodiment 11 of a data transmission method according to one embodiment of the present invention;

FIG. 17 is a schematic structural diagram of Embodiment 1 of a data transmission apparatus according to one embodiment of the present invention;

FIG. 18 is a schematic structural diagram of Embodiment 2 of a data transmission apparatus according to one embodiment of the present invention;

FIG. 19 is a schematic structural diagram of Embodiment 3 of a data transmission apparatus according to one embodiment of the present invention;

FIG. 20 is a schematic structural diagram of Embodiment 4 of a data transmission apparatus according to one embodiment of the present invention;

FIG. 21 is a schematic structural diagram of Embodiment 5 of a data transmission apparatus according to one embodiment of the present invention; and

FIG. 22 is a schematic structural diagram of Embodiment 6 of a data transmission apparatus according to one embodiment of the present invention.

DESCRIPTION OF EMBODIMENTS

The following clearly describes the technical solutions in the embodiments of the present invention with reference to the accompanying drawings in the embodiments of the present invention. Apparently, the described embodiments are merely some but not all of the embodiments of the present invention. All other embodiments obtained by persons of ordinary skill in the art based on the embodiments of the present invention without creative efforts shall fall within the protection scope of the present invention.

In the specification, claims, and accompanying drawings of the present invention, the terms “first”, “second”, “third”, “fourth”, and so on (if existent) are intended to distinguish between similar objects but do not necessarily indicate a specific order or sequence. It should be understood that the data termed in such a way is interchangeable in proper circumstances so that the embodiments of the present invention described herein can be implemented in orders except the order illustrated or described herein. Moreover, the terms “include”, “contain” and any other variants are intended to cover the non-exclusive inclusion, for example, a process, method, system, product, or device that includes a list of steps or units is not necessarily limited to those units, but may include other units not expressly listed or inherent to such a process, method, system, product, or device.

In the present invention, to improve transceiving performance of data transmission, both frequency diversity and space diversity are implemented by sending a signal.

An application scenario of the present invention is shown in FIG. 1. FIG. 1 is a schematic diagram of an application scenario according to one embodiment of the present invention, and FIG. 1 shows a schematic structural diagram of a 2×2 MIMO system. The system includes a transmitter and a receiver. The transmitter in the schematic structural diagram shown in FIG. 1 includes two transmit antennas, which are respectively a first transmit antenna M-1T and a second transmit antenna M-2T. The receiver includes two receive antennas, which are respectively a first receive antenna M-1R and a second receive antenna M-2R. There are four channels in total between the two transmit antennas and the two receive antennas, which are respectively 1-1 (a channel from the first transmit antenna to the first receive antenna), 1-2 (a channel from the first transmit antenna to the second receive antenna), 2-1 (a channel from the second transmit antenna to the first receive antenna), and 2-2 (a channel from the second transmit antenna to the second receive antenna).

Specific embodiments are used below to describe in detail the technical solutions of the present invention. The following several specific embodiments may be combined with each other, and the same or similar concept or process may not be described repeatedly in some embodiments.

FIG. 2 is a flowchart of a data transmission method according to one embodiment of the present invention. The method in this embodiment is executed by a transmitter, as shown in FIG. 2.

S201. Modulate information bits according to a lower order constellation diagram, and generate 4m lower order modulation symbols, where

m is an integer greater than or equal to 1.

S202. Separately multiply a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m higher order modulation symbols corresponding to a higher order constellation diagram.

The precoding matrix Q is obtained according to the 4m lower order modulation symbols and the higher order constellation diagram.

The higher order modulation symbols include some or all to-be-sent information bits.

For example:

For a quadrature phase shift keying (Quadrature Phase Shift Key, QPSK), the higher order modulation symbols include all the information bits. In a sending process, an information bit is sent on all transmit antennas and all subcarriers, for example, all symbols that are sent on a first subcarrier of a first transmit antenna, a second subcarrier of the first transmit antenna, a first subcarrier of a second transmit antenna, and a second subcarrier of the second transmit antenna include information about an information bit 1.

For an SQPSK, the higher order modulation symbols include half of the to-be-sent information bits. In a sending process, one information bit is sent on one subcarrier of all transmit antennas. If four information bits are sent, both a first subcarrier of a first transmit antenna and a second subcarrier of a second transmit antenna include information about an information bit 1 and an information bit 2, and both a second subcarrier of the first transmit antenna and a first subcarrier of the second transmit antenna include information about an information bit 3 and an information bit 4.

S203: Respectively send the 4m higher order modulation symbols on different carriers of two antennas.

The 4m higher order modulation symbols are classified into four types, a 4(i−1)+1^(th) higher order modulation symbol is a first higher order modulation symbol, a 4(i−1)+2^(th) higher order modulation symbol is a second higher order modulation symbol, a 4(i−1)+3^(th) higher order modulation symbol is a third higher order modulation symbol, and a 4(i−1)+4^(th) higher order modulation symbol is a fourth higher order modulation symbol, where 1≤i≤l, and i is an integer.

Specifically, the first higher order modulation symbol is sent on a first subcarrier of a first transmit antenna; the second higher order modulation symbol is sent on a first subcarrier of a second transmit antenna; the third higher order modulation symbol is sent on a second subcarrier of the first transmit antenna; and the fourth higher order modulation symbol is sent on a second subcarrier of the second transmit antenna.

In this embodiment of the present invention, the information bits are modulated according to the lower order constellation diagram, and the 4m lower order modulation symbols are generated; the precoding matrix Q is multiplied by the column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain the 4m higher order modulation symbols corresponding to the higher order constellation diagram; and the 4m higher order modulation symbols are respectively and correspondingly sent on the different carriers of the two antennas. The higher order modulation symbols include some or all information bits. Therefore, the same signal can be simultaneously sent on different carriers of multiple antennas, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

FIG. 3 and FIG. 4 show two methods executed by a receiver. A method in FIG. 3 is corresponding to a manner of joint demodulation, and a method in FIG. 4 is corresponding to a manner of performing independent demodulation and then performing combination. For details, refer to detailed descriptions of FIG. 3 and FIG. 4.

FIG. 3 is a flowchart of a data transmission method according to one embodiment of the present invention. The method in this embodiment is executed by the receiver, as shown in FIG. 3.

S301. Two receive antennas receive signals on two carriers.

The two receive antennas are respectively a first receive antenna and a second receive antenna, and the two carriers are respectively a first subcarrier and a second subcarrier. A signal received by the first receive antenna on the first subcarrier is r₁₁, a signal received by the second receive antenna on the first subcarrier is r₂₁, a signal received by the first receive antenna on the second subcarrier is r₁₂, and a signal received by the second receive antenna on the second subcarrier is r₂₂.

S302. Obtain 4m estimated values of lower order modulation symbols after channel equalization is performed on [r₁₁ r₂₁ r₁₂ r₂₂]^(T), where

m is an integer greater than or equal to 1.

S303. Demodulate the 4m estimated values of lower order modulation symbols according to a corresponding lower order constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

In this embodiment, the channel equalization is performed on a column vector including the signals that are received by the two receive antennas on different carriers, to obtain the 4m estimated values of lower order modulation symbols; the 4m estimated values of lower order modulation symbols are demodulated according to the corresponding lower order constellation diagram, to obtain the estimated value of the information bits sent by the transmit end; and the estimated value of the information bits sent by the transmit end is obtained in the manner of joint demodulation. The same signal can be simultaneously received by multiple receive antennas on different carriers, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

FIG. 4 is a flowchart of a data transmission method according to one embodiment of the present invention. The method in this embodiment is executed by the receiver, as shown in FIG. 4.

S401. Perform channel equalization on signals that are received by two antennas on a first subcarrier, to obtain 2m estimated values of first higher order modulation symbols, where

m is an integer greater than or equal to 1.

S402. Perform channel equalization on signals that are received by the two antennas on a second subcarrier, to obtain 2m estimated values of second higher order modulation symbols.

S403. Demodulate the 2m estimated values of first higher order modulation symbols in a mapping manner of a higher order constellation diagram, to obtain a first estimated value of information bits sent by a transmit end.

S404. Demodulate the 2m estimated values of second higher order modulation symbols in the mapping manner of the higher order constellation diagram, to obtain a second estimated value of the information bits sent by the transmit end.

S405. Combine the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end, to obtain an estimated value of the information bits sent by the transmit end.

In this embodiment, the channel equalization is performed on the signals that are received by the two antennas on the first subcarrier, to obtain the 2m estimated values of first higher order modulation symbols; the channel equalization is performed on the signals that are received by the two antennas on the second subcarrier, to obtain the 2m estimated values of second higher order modulation symbols; the 2m estimated values of first higher order modulation symbols are demodulated in the mapping manner of the higher order constellation diagram, to obtain the first estimated value of the information bits sent by the transmit end; the 2m estimated values of second higher order modulation symbols are demodulated in the mapping manner of the higher order constellation diagram, to obtain the second estimated value of the information bits sent by the transmit end; and the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end are combined, to obtain the estimated value of the information bits sent by the transmit end, that is, the estimated value of the information bits sent by the transmit end is obtained in the manner of performing independent demodulation and then performing combination. The same signal can be simultaneously received by multiple receive antennas on different carriers, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

The SQPSK and the QPSK are used as examples for detailed description in the following, and in the following embodiments, m=1 is used as an example for description.

1. A flowchart using the SQPSK as an example. A flowchart of a transmit end is shown in FIG. 5.

S501. Modulate four information bits according to a BPSK constellation diagram, and generate four BPSK symbols.

A binary phase shift keying (Binary Phase Shift Keying, BPSK for short) constellation diagram is shown in FIG. 6, the four information bits are respectively b₀, b₁, b₂, and b₃, and the four BPSK symbols are respectively s₀, s₁, s₂, and s₃, where s_(k)=2*b_(k)−1, and k=0, 1, 2, or 3.

S502. Multiply a precoding matrix Q by a column vector including the four BPSK symbols, to obtain four higher order modulation symbols corresponding to a QPSK constellation diagram.

The QPSK constellation diagram is shown in FIG. 6.

A precoding matrix

$Q = {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}$ is obtained according to four lower order modulation symbols and the QPSK constellation diagram, [s₀ s₁ s₂ s₃]^(T) is the column vector including the four BPSK symbols, the four higher order modulation symbols are respectively [x₀ x₁ x₂ x₃]^(T), and

$\begin{bmatrix} x_{0} \\ x_{1} \\ x_{2} \\ x_{3} \end{bmatrix} = {{{\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix}}.}$

S503. Send x₀ on a first subcarrier of a first transmit antenna; send x₁ on a first subcarrier of a second transmit antenna; send x₂ on a second subcarrier of the first transmit antenna; and send x₃ on a second subcarrier of the second transmit antenna.

In this embodiment, the four information bits are modulated according to the BPSK constellation diagram, and four BPSK symbols are generated; the precoding matrix Q is multiplied by the column vector including the four BPSK symbols, to obtain the four higher order modulation symbols corresponding to the QPSK constellation diagram; and x₀ is sent on the first subcarrier of the first transmit antenna, x₁ is sent on the first subcarrier of the second transmit antenna, x₂ is sent on the second subcarrier of the first transmit antenna, and x₃ is sent on the second subcarrier of the second transmit antenna. It can be learned that s₀ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both frequency diversity and space diversity are implemented; and s₁ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both the frequency diversity and the space diversity are implemented, so that transceiving performance of data transmission is improved.

There are two processing manners at a receive end. A first manner is shown in FIG. 8, and a second manner is shown in FIG. 9. The first manner is described first.

S801. Perform channel equalization on a column vector including signals that are received by two receive antennas on two carriers, to obtain four estimated values of BPSK symbols.

The column vector including signals that are received by the two receive antennas on the two carriers is

$\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix},$ and

${\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix} = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}{{\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix}}}},$ where r_(1,1) represents a signal received by a first receive antenna on a first subcarrier, r_(2,1) represents a signal received by a second receive antenna on the first subcarrier, r_(1,2) represents a signal received by the first receive antenna on a second subcarrier, and r_(2,2) represents a signal received by the second receive antenna on the second subcarrier. h_(11,1) represents a channel response that is from a first transmit antenna to the first receive antenna and that is on the first subcarrier; h_(12,1) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the first subcarrier; h_(21,1) represents a channel response that is from a second transmit antenna to the first receive antenna and that is on the first subcarrier; h_(22,1) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the first subcarrier; h_(11,2) represents a channel response that is from the first transmit antenna to the first receive antenna and that is on the second subcarrier; h_(12,2) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the second subcarrier; h_(21,2) represents a channel response that is from the second transmit antenna to the first receive antenna and that is on the second subcarrier; and h_(22,2) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the second subcarrier.

The four estimated values of BPSK symbols are respectively represented as ŝ₀, ŝ₁, ŝ₂, and ŝ₃, and

$\begin{bmatrix} {\hat{s}}_{0} \\ {\hat{s}}_{1} \\ {\hat{s}}_{2} \\ {\hat{s}}_{3} \end{bmatrix} = {{W\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix}}.}$

W is a channel equalization matrix. If a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ² I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, where

${G = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}Q}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion.

S802. Demodulate the four estimated values of BPSK modulation symbols in a mapping manner of a BPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

In this embodiment, the channel equalization is performed on the column vector including the signals that are received by the two receive antennas on the two carriers, to obtain the four estimated values of BPSK symbols; and the four estimated values of BPSK modulation symbols are demodulated in the mapping manner of the BPSK constellation diagram, to obtain the estimated value of the information bits sent by the transmit end, that is, the estimated value of the information bits sent by the transmit end is obtained in the manner of joint demodulation. The same signal can be simultaneously received by multiple receive antennas on different carriers, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

The second manner is shown in FIG. 9.

S901. Perform channel equalization on signals that are received by two antennas on a first subcarrier, to obtain two estimated values of first higher order modulation symbols.

The signals that are received by the two antennas on the first subcarrier may be represented as:

${\begin{bmatrix} r_{1,1} \\ r_{2,1} \end{bmatrix} = {\begin{bmatrix} h_{11,1} & h_{12,1} \\ h_{21,1} & h_{22,1} \end{bmatrix}\begin{bmatrix} x_{0} \\ x_{1} \end{bmatrix}}},$ where r_(1,1) represents a signal received by a first receive antenna on the first subcarrier, and r_(2,1) represents a signal received by a second receive antenna on the first subcarrier.

The channel equalization is performed on the signals

$\quad\begin{bmatrix} r_{1,1} \\ r_{2,1} \end{bmatrix}$ that are received on the first subcarrier, to obtain the two estimated values that are of the first higher order modulation symbols and that are respectively {circumflex over (x)}₁ and {circumflex over (x)}₂, and

${\begin{bmatrix} {\hat{x}}_{0} \\ {\hat{x}}_{1} \end{bmatrix} = {W\begin{bmatrix} r_{1,1} \\ r_{2,1} \end{bmatrix}}},$ where W is a channel equalization matrix. If a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ² I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, where

${G = \begin{bmatrix} h_{11,1} & h_{12,1} \\ h_{21,2} & h_{22,2} \end{bmatrix}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion.

S902. Perform channel equalization on signals that are received by the two antennas on a second subcarrier, to obtain two estimated values of second higher order modulation symbols.

The signals that are received by the two antennas on the second subcarrier may be represented as:

${\begin{bmatrix} r_{1,2} \\ r_{2,2} \end{bmatrix} = {\begin{bmatrix} h_{11,2} & h_{12,2} \\ h_{21,2} & h_{22,2} \end{bmatrix}\begin{bmatrix} x_{2} \\ x_{3} \end{bmatrix}}},$ where r_(1,2) represents a signal received by the first receive antenna on the second subcarrier, and r_(2,2) represents a signal received by the second receive antenna on the second subcarrier.

The channel equalization is performed on the signals

$\quad\begin{bmatrix} r_{1,2} \\ r_{2,2} \end{bmatrix}$ that are received on the second subcarrier, to obtain the two estimated values that are of the second higher order modulation symbols and that are respectively {circumflex over (x)}₂ and {circumflex over (x)}₃, and

${\begin{bmatrix} {\hat{x}}_{2} \\ {\hat{x}}_{3} \end{bmatrix} = {W\begin{bmatrix} r_{1,2} \\ r_{2,2} \end{bmatrix}}},$ where W is a channel equalization matrix. If a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ² I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, where

${G = \begin{bmatrix} h_{11,2} & h_{12,2} \\ h_{21,2} & h_{22,2} \end{bmatrix}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion.

S903. Demodulate the two estimated values of first higher order modulation symbols in a mapping manner of a QPSK constellation diagram, to obtain a first estimated value of information bits sent by a transmit end.

The first estimated value may be represented as:

{circumflex over (b)}₀, {circumflex over (b)}₁, {circumflex over (b)}₂, and {circumflex over (b)}₃.

S904. Demodulate the two estimated values of second higher order modulation symbols in the mapping manner of the QPSK constellation diagram, to obtain a second estimated value of the information bits sent by the transmit end.

The second estimated value may be represented as:

b ₀, b ₁, b ₂, and b ₃.

S905. Combine the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end, to obtain an estimated value of the information bits sent by the transmit end.

The estimated value of the information bits sent by the transmit end is {tilde over (b)}₀, {tilde over (b)}₁, {tilde over (b)}₂, or {tilde over (b)}₃, where {tilde over (b)}_(k)=({circumflex over (b)}_(k)+{circumflex over (b)}_(k))/2, and k=0, 1, 2, or 3.

In this embodiment, the channel equalization is performed on the signals that are received by the two antennas on the first subcarrier, to obtain the two estimated values of first higher order modulation symbols; the channel equalization is performed on the signals that are received by the two antennas on the second subcarrier, to obtain the two estimated values of second higher order modulation symbols; the two estimated values of first higher order modulation symbols are demodulated in the mapping manner of the QPSK constellation diagram, to obtain the first estimated value of the information bits sent by the transmit end; the two estimated values of second higher order modulation symbols are demodulated in the mapping manner of the QPSK constellation diagram, to obtain the second estimated value of the information bits sent by the transmit end; and the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end are combined, to obtain the estimated value of the information bits sent by the transmit end, that is, the estimated value of the information bits sent by the transmit end is obtained in the manner of performing independent demodulation and then performing combination. The same signal can be simultaneously received by multiple receive antennas on different carriers, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

2. A flowchart using the QPSK as an example. Implementations of the QPSK are classified into two types, a higher order constellation diagram of a first implementation is a 256 quadrature amplitude modulation (Quadrature Amplitude Modulation, QAM for short) constellation diagram, and a higher order constellation diagram of a second implementation is a 128QAM constellation diagram.

In one embodiment, a flowchart at a transmit end is shown in FIG. 10.

S1001. Modulate eight information bits according to a QPSK constellation diagram, and generate four QPSK symbols.

The QPSK constellation diagram is shown in FIG. 7, the eight information bits are respectively b_(k), where k=0, 1, . . . , or 7, and the four QPSK symbols are respectively s₀, s₁, s₂, and s₃, where s_(k)=(2*b_(2k)−1)+j(2*b_(2k+1)−1), and k=0, 1, 2, or 3.

S1002. Multiply a precoding matrix Q by a column vector including the four QPSK symbols, to obtain four higher order modulation symbols corresponding to a 256QAM constellation diagram.

The 256QAM constellation diagram is shown in FIG. 11, and a precoding matrix

$Q = {\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}$ is obtained according to four lower order modulation symbols and the 256QAM constellation diagram.

Specifically, one 256QAM symbol can be split into combinations of the four QPSK symbols, that is, s=(±8)*s₀+(±4)*s₁+(±2)*s₂+(±1)*s₃. A coefficient combination (±8, ±4, ±2, ±1) is used as a start point for finding a combination Q that can generate an orthogonal matrix.

It is easy to learn that the coefficient combination (±8, ±4, ±2, ±1) may generate 384 different row vectors, and a generation method is as follows:

(1) 16 row vectors are first generated in the following according to an order of (±8, ±4, ±2, ±1):

(8, 4, 2, 1), (8, 4, 2, −1), (8, 4, −2, 1), (8, 4, −2, −1), (8, −4, 2, 1), (8, −4, 2, −1), (8, −4, −2, 1), (8, −4, −2, −1), (−8, 4, 2, 1), (−8, 4, 2, −1), (−8, 4, −2, 1), (−8, 4, −2, −1), (−8, −4, 2, 1), (−8, −4, 2, −1), (−8, −4, −2, 1), and (−8, −4, −2, −1).

Cyclic shift is performed on the foregoing generated 16 vectors, and 64 row vectors are generated. (8, 4, 2, 1) is used as an example, and four row vectors can be generated: (8, 4, 2, 1), (1, 8, 4, 2), (2, 1, 8, 4), and (4, 2, 1, 8). By analogy, 64 row vectors can be generated in total.

(2) Further, 64×5 row vectors are generated in the following according to an order of (±8, ±4, ±1, ±2), (±8, ±2, ±4, ±1), (±8, ±2, ±1, ±4), (±8, ±1, ±2, ±4), and (±8, ±1, ±4, ±2).

Generally, a value of a first row vector is first fixed at (8, 4, −2, 1), and then the remaining 383 row vectors are searched for a row vector orthogonal to the first row vector, and the found row vector is (4, −8, 1, 2). After the first row vector and a second row vector are determined, the remaining 382 row vectors are searched for a row vector orthogonal to both the first row vector and the second row vector, and a value of the found row vector is (2, 1, 8, −4). By analogy, the remaining 381 row vectors are searched for a row vector orthogonal to the first row vector, the second row vector, and the third row vector, and a value of the found row vector is (1, −2, −4, −8).

$\quad\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix}$ is the column vector including the four QPSK symbols, and the four higher order modulation symbols are respectively x₁, x₂, x₃, and x₄, and

$\begin{bmatrix} x_{0} \\ x_{1} \\ x_{2} \\ x_{3} \end{bmatrix} = {{{\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix}}.}$

S1003. Send x₀ on a first subcarrier of a first transmit antenna; send x₁ on a first subcarrier of a second transmit antenna; send x₂ on a second subcarrier of the first transmit antenna; and send x₃ on a second subcarrier of the second transmit antenna.

In this embodiment, the eight information bits are modulated according to the QPSK constellation diagram, and four QPSK symbols are generated; the precoding matrix Q is multiplied by the column vector including the four QPSK symbols, to obtain the four higher order modulation symbols corresponding to the 256QAM constellation diagram; and x₀ is sent on the first subcarrier of the first transmit antenna, x₁ is sent on the first subcarrier of the second transmit antenna, x₂ is sent on the second subcarrier of the first transmit antenna, and x₃ is sent on the second subcarrier of the second transmit antenna. It can be learned that s₀ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both frequency diversity and space diversity are implemented; s₁ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both the frequency diversity and the space diversity are implemented; s₂ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both the frequency diversity and the space diversity are implemented; and s₃ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both the frequency diversity and the space diversity are implemented, so that transceiving performance of data transmission is improved.

In the first implementation, there are two processing manners at a receive end. A first manner is shown in FIG. 12, and a second manner is shown in FIG. 13. The first manner is described first.

As shown in FIG. 12:

S1201. Perform channel equalization on a column vector including signals that are received by two receive antennas on two carriers, to obtain four estimated values of QPSK symbols.

The column vector including signals that are received by the two receive antennas on the two carriers is

$\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix},$ and

${\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix} = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}{{\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix}}}},$ where r_(1,1) represents a signal received by a first receive antenna on a first subcarrier, r_(2,1) represents a signal received by a second receive antenna on the first subcarrier, r_(1,2) represents a signal received by the first receive antenna on a second subcarrier, and r_(2,2) represents a signal received by the second receive antenna on the second subcarrier. h_(11,1) represents a channel response that is from a first transmit antenna to the first receive antenna and that is on the first subcarrier; h_(12,1) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the first subcarrier; h_(21,1) represents a channel response that is from a second transmit antenna to the first receive antenna and that is on the first subcarrier; h_(22,1) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the first subcarrier; h_(11,2) represents a channel response that is from the first transmit antenna to the first receive antenna and that is on the second subcarrier; h_(12,2) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the second subcarrier; h_(21,2) represents a channel response that is from the second transmit antenna to the first receive antenna and that is on the second subcarrier; and h_(22,2) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the second subcarrier.

The four estimated values of QPSK symbols are respectively represented as ŝ₀, ŝ₁, ŝ₂, and ŝ₃, and

$\begin{bmatrix} {\hat{s}}_{0} \\ {\hat{s}}_{1} \\ {\hat{s}}_{2} \\ {\hat{s}}_{3} \end{bmatrix} = {{W\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix}}.}$

W is a channel equalization matrix. If a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ² I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, where

${G = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}Q}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion.

S1202. Demodulate the four estimated values of QPSK modulation symbols in a mapping manner of a QPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

In this embodiment, the channel equalization is performed on the column vector including the signals that are received by the two receive antennas on the two carriers, to obtain the four estimated values of QPSK symbols; and the four estimated values of QPSK modulation symbols are demodulated in the mapping manner of the QPSK constellation diagram, to obtain the estimated value of the information bits sent by the transmit end, that is, the estimated value of the information bits sent by the transmit end is obtained in the manner of joint demodulation. The same signal can be simultaneously received by multiple receive antennas on different carriers, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

The second manner:

As shown in FIG. 13:

S1301. Perform channel equalization on signals that are received by two antennas on a first subcarrier, to obtain two estimated values of first higher order modulation symbols.

The signals that are received by the two antennas on the first subcarrier may be represented as:

${\begin{bmatrix} r_{1,1} \\ r_{2,1} \end{bmatrix} = {\begin{bmatrix} h_{11,1} & h_{12,1} \\ h_{21,1} & h_{22,1} \end{bmatrix}\begin{bmatrix} x_{0} \\ x_{1} \end{bmatrix}}},$ where r_(1,1) represents a signal received by a first receive antenna on the first subcarrier, and r_(2,1) represents a signal received by a second receive antenna on the first subcarrier.

The channel equalization is performed on the signals

$\quad\begin{bmatrix} r_{1,1} \\ r_{2,1} \end{bmatrix}$ that are received on the first subcarrier, to obtain the two estimated values that are of the first higher order modulation symbols and that are respectively {circumflex over (x)}₀ and {circumflex over (x)}₁, and

${\begin{bmatrix} {\hat{x}}_{0} \\ {\hat{x}}_{1} \end{bmatrix} = {W\begin{bmatrix} r_{1,1} \\ r_{2,1} \end{bmatrix}}},$ where W is a channel equalization matrix. If a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ² I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, where

${G = \begin{bmatrix} h_{11,1} & h_{12,1} \\ h_{21,2} & h_{22,2} \end{bmatrix}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion.

S1302. Perform channel equalization on signals that are received by the two antennas on a second subcarrier, to obtain two estimated values of second higher order modulation symbols.

The signals that are received by the two antennas on the second subcarrier may be represented as:

${\begin{bmatrix} r_{1,1} \\ r_{2,1} \end{bmatrix} = {\begin{bmatrix} h_{11,2} & h_{12,2} \\ h_{21,2} & h_{22,2} \end{bmatrix}\begin{bmatrix} x_{2} \\ x_{3} \end{bmatrix}}},$ where r_(1,2) represents a signal received by the first receive antenna on the second subcarrier, and r_(2,2) represents a signal received by the second receive antenna on the second subcarrier.

The channel equalization is performed on the signals

$\quad\begin{bmatrix} r_{1,2} \\ r_{2,2} \end{bmatrix}$ that are received on the second subcarrier, to obtain the two estimated values that are of the second higher order modulation symbols and that are respectively {circumflex over (x)}₂ and {circumflex over (x)}₃, and

${\begin{bmatrix} {\hat{x}}_{2} \\ {\hat{x}}_{3} \end{bmatrix} = {W\begin{bmatrix} r_{1,2} \\ r_{2,2} \end{bmatrix}}},$ where W is a channel equalization matrix. If a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ² I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, where

${G = \begin{bmatrix} h_{11,2} & h_{12,2} \\ h_{21,2} & h_{22,2} \end{bmatrix}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion.

S1303. Demodulate the two estimated values of first higher order modulation symbols in a mapping manner of a 256QAM constellation diagram, to obtain a first estimated value of information bits sent by a transmit end.

The first estimated value may be represented as:

{circumflex over (b)}₀, {circumflex over (b)}₁, {circumflex over (b)}₂, {circumflex over (b)}₃, {circumflex over (b)}₄, {circumflex over (b)}₅, {circumflex over (b)}₆, and {circumflex over (b)}₇.

S1304. Demodulate the two estimated values of second higher order modulation symbols in the mapping manner of the 256QAM constellation diagram, to obtain a second estimated value of the information bits sent by the transmit end.

The second estimated value may be represented as:

b ₀, b ₁, b ₂, b ₃, b ₄, b ₅, b ₆, and b ₇.

S1305. Combine the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end, to obtain an estimated value of the information bits sent by the transmit end.

The estimated value of the information bits sent by the transmit end is {tilde over (b)}₀, {tilde over (b)}₁, {tilde over (b)}₂, {tilde over (b)}₃,

,

,

, or

, where {tilde over (b)}_(k)=({circumflex over (b)}_(k)+{circumflex over (b)}_(k))/2, and k=0, 1, 2, 3, 4, 5, 6, or 7.

In this embodiment, the channel equalization is performed on the signals that are received by the two antennas on the first subcarrier, to obtain the two estimated values of first higher order modulation symbols; the channel equalization is performed on the signals that are received by the two antennas on the second subcarrier, to obtain two estimated values of second higher order modulation symbols; the two estimated values of first higher order modulation symbols are demodulated in the mapping manner of the 256QAM constellation diagram, to obtain the first estimated value of the information bits sent by the transmit end; the two estimated values of second higher order modulation symbols are demodulated in the mapping manner of the 256QAM constellation diagram, to obtain the second estimated value of the information bits sent by the transmit end; and the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end are combined, to obtain the estimated value of the information bits sent by the transmit end, that is, the estimated value of the information bits sent by the transmit end is obtained in the manner of performing independent demodulation and then performing combination. The same signal can be simultaneously received by multiple receive antennas on different carriers, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

In one embodiment, a flowchart at a transmit end is shown in FIG. 14.

S1401. Modulate eight information bits according to a QPSK constellation diagram, and generate four QPSK symbols.

The QPSK constellation diagram is shown in FIG. 7, the eight information bits are respectively b_(k), where k=0, 1, . . . , or 7, and the four QPSK symbols are respectively s₀, s₁, s₂, and s₃, where s_(k)=(2*b_(2k)−1)+j(2*b_(2k+1)−1), and k=0, 1, 2, or 3.

S1402. Multiply a precoding matrix Q by a column vector including the four QPSK symbols, to obtain four higher order modulation symbols corresponding to a 128QAM constellation diagram.

The 128QAM constellation diagram is shown in FIG. 15, and a precoding matrix

$Q = {\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\;\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\;\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\;\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\;\pi}} \end{bmatrix}}$ is obtained according to four lower order modulation symbols and the 128QAM constellation diagram. Specifically, the 128QAM constellation diagram is similar to the 256QAM constellation diagram, but a difference lies in that a coefficient combination is (±1, ±1, ±1, e^(±j0.25π)).

$\quad\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix}$ is the column vector including the four QPSK symbols, and the four to-be-sent higher order modulation symbols are respectively x₀, x₁, x₂, and x₃, and

$\begin{bmatrix} x_{0} \\ x_{1} \\ x_{2} \\ x_{3} \end{bmatrix} = {{\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\;\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\;\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\;\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\;\pi}} \end{bmatrix}}{\quad{\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix}.}}}$

S1403. Send x₀ on a first subcarrier of a first transmit antenna; send x₁ on a first subcarrier of a second transmit antenna; send x₂ on a second subcarrier of the first transmit antenna; and send x₃ on a second subcarrier of the second transmit antenna.

In this embodiment, the eight information bits are modulated according to the QPSK constellation diagram, and four QPSK symbols are generated; the precoding matrix Q is multiplied by the column vector including the four QPSK symbols, to obtain the four higher order modulation symbols corresponding to the 128QAM constellation diagram; and x₀ is sent on the first subcarrier of the first transmit antenna, x₁ is sent on the first subcarrier of the second transmit antenna, x₂ is sent on the second subcarrier of the first transmit antenna, and x₃ is sent on the second subcarrier of the second transmit antenna. It can be learned that s₀ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both frequency diversity and space diversity are implemented; s₁ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both the frequency diversity and the space diversity are implemented; s₂ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both the frequency diversity and the space diversity are implemented; and s₃ is simultaneously sent on the first subcarrier and the second subcarrier, and sent on the first transmit antenna and the second transmit antenna, and both the frequency diversity and the space diversity are implemented, so that transceiving performance of data transmission is improved.

A processing manner at the receive end is shown in FIG. 16 according to one embodiment.

S1601. Perform channel equalization on a column vector including signals that are received by two receive antennas on two carriers, to obtain four estimated values of QPSK symbols.

The column vector including signals that are received by the two receive antennas on the two carriers is

$\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix},$ and

$\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix} = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}{\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\;\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\;\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\;\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\;\pi}} \end{bmatrix}}{\quad{\begin{bmatrix} s_{0} \\ s_{1} \\ s_{2} \\ s_{3} \end{bmatrix},}}}$ where r_(1,1) represents a signal received by a first receive antenna on a first subcarrier, r_(2,1) represents a signal received by a second receive antenna on the first subcarrier, r_(1,2)represents a signal received by the first receive antenna on a second subcarrier, and r_(2,2) represents a signal received by the second receive antenna on the second subcarrier. h_(11,1) represents a channel response that is from a first transmit antenna to the first receive antenna and that is on the first subcarrier; h_(12,1) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the first subcarrier; h_(21,1) represents a channel response that is from a second transmit antenna to the first receive antenna and that is on the first subcarrier; h_(22,1) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the first subcarrier; h_(11,2) represents a channel response that is from the first transmit antenna to the first receive antenna and that is on the second subcarrier; h_(12,2) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the second subcarrier; h_(21,2) represents a channel response that is from the second transmit antenna to the first receive antenna and that is on the second subcarrier; and h_(22,2) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the second subcarrier.

The four estimated values of QPSK symbols are respectively represented as ŝ₀, ŝ₁, ŝ₂, and ŝ₃, and

$\begin{bmatrix} {\overset{\hat{}}{s}}_{o} \\ {\overset{\hat{}}{s}}_{1} \\ {\overset{\hat{}}{s}}_{2} \\ {\overset{\hat{}}{s}}_{3} \end{bmatrix} = {{W\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix}}.}$

W is a channel equalization matrix. If a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ² I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, where

${G = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}Q}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion.

S1602. Demodulate the four estimated values of QPSK modulation symbols in a mapping manner of a QPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

In this embodiment, the channel equalization is performed on the column vector including the signals that are received by the two receive antennas on the two carriers, to obtain the four estimated values of QPSK symbols; and the four estimated values of QPSK modulation symbols are demodulated in the mapping manner of the QPSK constellation diagram, to obtain the estimated value of the information bits sent by the transmit end, that is, the estimated value of the information bits sent by the transmit end is obtained in the manner of joint demodulation. The same signal can be simultaneously received by multiple receive antennas on different carriers, and frequency diversity and space diversity are implemented, so that transceiving performance of data transmission is improved.

FIG. 17 is a schematic structural diagram of Embodiment 1 of a data transmission apparatus according to the present invention. As shown in FIG. 17, the apparatus in this embodiment includes a modulation module 1701, a processing module 1702, and a sending module 1703. The modulation module 1701 is configured to modulate to-be-sent information bits according to a lower order constellation diagram, and generate 4m lower order modulation symbols, where m is an integer greater than or equal to 1. The processing module 1702 is configured to separately multiply a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m to-be-sent higher order modulation symbols corresponding to a higher order constellation diagram. The sending module 1703 is configured to respectively and correspondingly send the 4m to-be-sent higher order modulation symbols on different carriers of two antennas.

In the foregoing embodiment, the 4m higher order modulation symbols are classified into four types, a 4(i−1)+1^(th) higher order modulation symbol is a first higher order modulation symbol, a 4(i−1)+2^(th) higher order modulation symbol is a second higher order modulation symbol, a 4(i−1)+3^(th) higher order modulation symbol is a third higher order modulation symbol, and a 4(i−1)+4^(th) higher order modulation symbol is a fourth higher order modulation symbol, where 1≤i≤l, and i is an integer.

The sending module is configured to send the first higher order modulation symbol on a first subcarrier of a first transmit antenna; send the second higher order modulation symbol on a first subcarrier of a second transmit antenna; send the third higher order modulation symbol on a second subcarrier of the first transmit antenna; and send the fourth higher order modulation symbol on a second subcarrier of the second transmit antenna.

In the foregoing embodiment, the processing module 1702 is configured to:

multiply a precoding matrix

$Q = {\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four quadrature phase shift keying QPSK symbols, to obtain four to-be-sent 256QAM modulation symbols that are corresponding to a 256 quadrature amplitude modulation QAM constellation diagram and that are respectively [x₀ x₁ x₂ x₃]^(T), where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, x₃ is the fourth higher order modulation symbol, and [ ]^(T) represents transpose.

In the foregoing embodiment, the processing module 1702 is configured to:

multiply a precoding matrix

$Q = {\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\;\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\;\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\;\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\;\pi}} \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four QPSK symbols, to obtain four 128QAM modulation symbols that are corresponding to a 128QAM constellation diagram and that are respectively [x₀ x₁ x₂ x₃]^(T), where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, x₃ is the fourth higher order modulation symbol, and [ ]^(T) represents transpose.

In the foregoing embodiment, the processing module 1702 is configured to:

multiply a precoding matrix

$Q = {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}$ by a column vector [s₀ s₁ s₂ s₃]^(T) including four BPSK symbols, to obtain four modulation symbols that are corresponding to a QPSK constellation diagram and that are respectively [x₀ x₁ x₂ x₃]^(T), where x₀ is the first higher order modulation symbol, x₁ is the second higher order modulation symbol, x₂ is the third higher order modulation symbol, and x₃ is the fourth higher order modulation symbol.

The apparatus in this embodiment may be correspondingly configured to implement the technical solution in the method embodiment shown in FIG. 5, FIG. 10, or FIG. 14, and implementation principles and technical effects of the apparatus are similar and are not described herein again.

FIG. 18 is a structural diagram of a data transmission apparatus according to one embodiment of the present invention. As shown in FIG. 18, the apparatus in this embodiment includes a receiving module 1801, a channel equalization module 1802, and a demodulation module 1803. The receiving module 1801 is configured to receive signals on two carriers, where the receiving module is deployed on a first receive antenna and a second receive antenna, the two carriers are respectively a first subcarrier and a second subcarrier, and a signal received by the first receive antenna on the first subcarrier is r₁₁, a signal received by the second receive antenna on the first subcarrier is r₂₁, a signal received by the first receive antenna on the second subcarrier is r₁₂, and a signal received by the second receive antenna on the second subcarrier is r₂₂. The channel equalization module 1802 is configured to obtain 4m estimated values of lower order modulation symbols after channel equalization is performed on [r₁₁ r₂₁ r₁₂ r₂₂]^(T), where m is an integer greater than or equal to 1. The demodulation module 1803 is configured to demodulate the 4m estimated values of lower order modulation symbols according to a corresponding lower order constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

In the foregoing embodiment, the lower order modulation symbol is a quadrature phase shift keying QPSK modulation symbol or a binary phase shift keying BPSK modulation symbol.

The apparatus in this embodiment may be correspondingly configured to implement the technical solution in the method embodiment shown in FIG. 8 or FIG. 12, and implementation principles and technical effects of the apparatus are similar and are not described herein again.

FIG. 19 is a structural diagram of a data transmission apparatus according to one embodiment of the present invention. As shown in FIG. 19, the apparatus in this embodiment includes a channel equalization module 1901, a demodulation module 1902, and a processing module 1903. The channel equalization module 1901 is configured to perform channel equalization on signals that are received by two antennas on a first subcarrier, to obtain 2m estimated values of first higher order modulation symbols, where m is an integer greater than or equal to 1; and the channel equalization module 1901 is further configured to perform channel equalization on signals that are received by the two antennas on a second subcarrier, to obtain 2m estimated values of second higher order modulation symbols. The demodulation module 1902 is configured to demodulate the 2m estimated values of first higher order modulation symbols in a mapping manner of a higher order constellation diagram, to obtain a first estimated value of information bits sent by a transmit end; and the demodulation module 1902 is further configured to demodulate the 2m estimated values of second higher order modulation symbols in the mapping manner of the higher order constellation diagram, to obtain a second estimated value of the information bits sent by the transmit end. The processing module 1903 is configured to combine the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end, to obtain an estimated value of the information bits sent by the transmit end.

In the foregoing embodiment, the higher order modulation symbol is a 256 quadrature amplitude modulation QAM modulation symbol or a quadrature phase shift keying QPSK modulation symbol.

The apparatus in this embodiment may be correspondingly configured to implement the technical solution in the method embodiment shown in FIG. 9, FIG. 13, or FIG. 16, and implementation principles and technical effects of the apparatus are similar and are not described herein again.

FIG. 20 is a structural diagram of a data transmission apparatus according to one embodiment of the present invention. As shown in FIG. 20, the apparatus in this embodiment includes a modulator 2001, a processor 2002, and a transmitter 2003. The modulator 2001 is configured to modulate to-be-sent information bits according to a lower order constellation diagram, and generate 4m lower order modulation symbols, where m is an integer greater than or equal to 1. The processor 2002 is configured to separately multiply a precoding matrix Q by a column vector including every four lower order modulation symbols in the 4m lower order modulation symbols, to obtain 4m to-be-sent higher order modulation symbols corresponding to a higher order constellation diagram. The transmitter 2003 is configured to respectively and correspondingly send the 4m to-be-sent higher order modulation symbols on different carriers of two antennas.

The apparatus in this embodiment may be correspondingly configured to implement the technical solution in the method embodiment shown in FIG. 5, FIG. 10, or FIG. 14, and implementation principles and technical effects of the apparatus are similar and are not described herein again.

FIG. 21 is a structural diagram of a data transmission apparatus according to one embodiment of the present invention. The apparatus in this embodiment includes a receiver 2101, a channel equalizer 2102, and a demodulator 2103. The receiver 2101 is configured to receive signals on two carriers, where the receivers are deployed on a first receive antenna and a second receive antenna, the two carriers are respectively a first subcarrier and a second subcarrier, and a signal received by the first receive antenna on the first subcarrier is r₁₁, a signal received by the second receive antenna on the first subcarrier is r₂₁, a signal received by the first receive antenna on the second subcarrier is r₁₂, and a signal received by the second receive antenna on the second subcarrier is r₂₂.

The channel equalizer 2102 is configured to obtain 4m estimated values of lower order modulation symbols after channel equalization is performed on [r₁₁ r₂₁ r₁₂ r₂₂]^(T), where m is an integer greater than or equal to 1. The demodulator 2103 is configured to demodulate the 4m estimated values of lower order modulation symbols according to a corresponding lower order constellation diagram, to obtain an estimated value of information bits sent by a transmit end.

The apparatus in this embodiment may be correspondingly configured to implement the technical solution in the method embodiment shown in FIG. 8 or FIG. 12, and implementation principles and technical effects of the apparatus are similar and are not described herein again.

FIG. 22 is a structural diagram of a data transmission apparatus according to one embodiment of the present invention. The apparatus in this embodiment includes a channel equalizer 2201, a demodulator 2202, and a processor 2203. The channel equalizer 2201 is configured to perform channel equalization on signals that are received by two antennas on a first subcarrier, to obtain 2m estimated values of first higher order modulation symbols, where m is an integer greater than or equal to 1; and the channel equalizer 2201 is further configured to perform channel equalization on signals that are received by the two antennas on a second subcarrier, to obtain 2m estimated values of second higher order modulation symbols. The demodulator 2202 is configured to demodulate the 2m estimated values of first higher order modulation symbols in a mapping manner of a higher order constellation diagram, to obtain a first estimated value of information bits sent by a transmit end; and the demodulator 2202 is further configured to demodulate the 2m estimated values of second higher order modulation symbols in the mapping manner of the higher order constellation diagram, to obtain a second estimated value of the information bits sent by the transmit end. The processor 2203 is configured to combine the first estimated value of the information bits sent by the transmit end and the second estimated value of the information bits sent by the transmit end, to obtain an estimated value of the information bits sent by the transmit end.

The apparatus in this embodiment may be correspondingly configured to implement the technical solution in the method embodiment shown in FIG. 9, FIG. 13, or FIG. 16, and implementation principles and technical effects of the apparatus are similar and are not described herein again.

Persons of ordinary skill in the art may understand that all or some of the steps of the method embodiments may be implemented by a program instructing relevant hardware. The program may be stored in a computer-readable storage medium. When the program runs, the steps of the method embodiments are performed. The foregoing storage medium includes: any medium that can store program code, such as a ROM, a RAM, a magnetic disk, or an optical disc.

Finally, it should be noted that the foregoing embodiments are merely intended for describing the technical solutions of the present invention, but not for limiting the present invention. Although the present invention is described in detail with reference to the foregoing embodiments, persons of ordinary skill in the art should understand that they may still make modifications to the technical solutions described in the foregoing embodiments or make equivalent replacements to some or all technical features thereof, without departing from the scope of the technical solutions of the embodiments of the present invention. 

The invention claimed is:
 1. A data transmission method, comprising: receiving, by two receive antennas, signals on two carriers, wherein a signal received by a first receive antenna on a first subcarrier is r₁₁, a signal received by a second receive antenna on the first subcarrier is r₂₁, a signal received by the first receive antenna on a second subcarrier is r₁₂, and a signal received by the second receive antenna on the second subcarrier is r₂₂, wherein the two receive antennas comprise the first receive antenna and the second receive antenna, and the two carriers comprise the first subcarrier and the second subcarrier; obtaining 4m estimated values of lower order modulation symbols after channel equalization is performed on [r₁₁ r₂₁ r₁₂ r₂₂]T, wherein m is an integer greater than or equal to 1; and demodulating the 4m estimated values of lower order modulation symbols according to a corresponding lower order constellation diagram, to obtain an estimated value of information bits sent by a transmit end.
 2. The method according to claim 1, wherein the lower order modulation symbols are quadrature phase shift keying (QPSK) modulation symbols or binary phase shift keying (BPSK) modulation symbols.
 3. The method according to claim 1, wherein m is equal to 1, the 4m estimated values of lower order modulation symbols are respectively represented as ŝ₀, ŝ₁, ŝ₂, and ŝ₃, and ${\begin{bmatrix} {\overset{\hat{}}{s}}_{0} \\ {\overset{\hat{}}{s}}_{1} \\ {\overset{\hat{}}{s}}_{2} \\ {\overset{\hat{}}{s}}_{3} \end{bmatrix} = {W\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix}}},$ wherein W is a channel equalization matrix, if a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ²I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, wherein ${G = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}Q}},$ δ₂ is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion, wherein h_(11,1) represents a channel response that is from a first transmit antenna to the first receive antenna and that is on the first subcarrier; h_(12,1) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the first subcarrier; h_(21,1) represents a channel response that is from a second transmit antenna to the first receive antenna and that is on the first subcarrier; h_(22,1) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the first subcarrier; h_(11,2) represents a channel response that is from the first transmit antenna to the first receive antenna and that is on the second subcarrier; h_(12,2) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the second subcarrier; h_(21,2) represents a channel response that is from the second transmit antenna to the first receive antenna and that is on the second subcarrier; and h_(22,2) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the second subcarrier, wherein Q is a precoding matrix.
 4. The method according to claim 3, wherein the lower order modulation symbols are binary phase shift keying (BPSK) symbols, the precoding matrix ${Q = {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}},$ and demodulating the 4m estimated values of the BPSK modulation symbols in a mapping manner of a BPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.
 5. The method according to claim 3, wherein the lower order modulation symbols are quadrature phase shift keying (QPSK) symbols, the precoding matrix ${Q = {\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}},$ and demodulating the 4m estimated values of the QPSK modulation symbols in a mapping manner of a QPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.
 6. The method according to claim 3, wherein the lower order modulation symbols are quadrature phase shift keying (QPSK) symbols, the precoding matrix ${Q = {\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\;\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\;\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\;\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\;\pi}} \end{bmatrix}}},$ and demodulating the 4m estimated values of the QPSK modulation symbols in a mapping manner of a QPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.
 7. A data transmission apparatus, comprising: a receiver deployed on a first receive antenna and a second receive antenna, and configured to receive signals on two carriers that comprise a first subcarrier and a second subcarrier, wherein a signal received by the first receive antenna on the first subcarrier is r₁₁, a signal received by the second receive antenna on the first subcarrier is r₂₁, a signal received by the first receive antenna on the second subcarrier is r₁₂, and a signal received by the second receive antenna on the second subcarrier is r₂₂; a channel equalizer, configured to obtain 4m estimated values of lower order modulation symbols after channel equalization is performed on [r₁₁ r₂₁ r₁₂ r₂₂]T, wherein m is an integer greater than or equal to 1; and a demodulator, configured to demodulate the 4m estimated values of lower order modulation symbols according to a corresponding lower order constellation diagram, to obtain an estimated value of information bits sent by a transmit end.
 8. The apparatus according to claim 7, wherein the lower order modulation symbol is a quadrature phase shift keying (QPSK) modulation symbol or a binary phase shift keying (BPSK) modulation symbol.
 9. The apparatus according to claim 7, wherein m is equal to 1, the 4m estimated values of lower order modulation symbols are respectively represented as ŝ₀, ŝ₁, ŝ₂, and ŝ₃, and ${\begin{bmatrix} {\overset{\hat{}}{s}}_{0} \\ {\overset{\hat{}}{s}}_{1} \\ {\overset{\hat{}}{s}}_{2} \\ {\overset{\hat{}}{s}}_{3} \end{bmatrix} = {W\begin{bmatrix} r_{1,1} \\ r_{2,1} \\ r_{1,2} \\ r_{2,2} \end{bmatrix}}},$ wherein W is a channel equalization matrix, if a linear minimum mean square error method is used, a corresponding channel equalization matrix is W=(G^(H)G+δ²I₄)⁻¹G^(H); or if a zero forcing method is used, a corresponding channel equalization matrix is W=G⁻¹, wherein ${G = {\begin{bmatrix} h_{11,1} & h_{12,1} & 0 & 0 \\ h_{21,1} & h_{22,1} & 0 & 0 \\ 0 & 0 & h_{11,2} & h_{12,2} \\ 0 & 0 & h_{21,2} & h_{22,2} \end{bmatrix}Q}},$ δ² is noise power, I₄ is a fourth-order identity matrix, and ( )⁻¹ represents matrix inversion, wherein h_(11,1) represents a channel response that is from a first transmit antenna to the first receive antenna and that is on the first subcarrier; h_(12,1) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the first subcarrier; h_(21,1) represents a channel response that is from a second transmit antenna to the first receive antenna and that is on the first subcarrier; h_(22,1) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the first subcarrier; h_(11,2) represents a channel response that is from the first transmit antenna to the first receive antenna and that is on the second subcarrier; h^(12,2) represents a channel response that is from the first transmit antenna to the second receive antenna and that is on the second subcarrier; h_(21,2) represents a channel response that is from the second transmit antenna to the first receive antenna and that is on the second subcarrier; and h_(22,2) represents a channel response that is from the second transmit antenna to the second receive antenna and that is on the second subcarrier, wherein Q is a precoding matrix.
 10. The apparatus according to claim 9, wherein the lower order modulation symbols are binary phase shift keying (BPSK) symbols, the precoding matrix ${Q = {\frac{1}{\sqrt{2}}\begin{bmatrix} 1 & j & 0 & 0 \\ 0 & 0 & 1 & {- j} \\ 1 & {- j} & 0 & 0 \\ j & 1 & 0 & 0 \end{bmatrix}}},$ and wherein the demodulator is configured to demodulate the 4m estimated values of the BPSK modulation symbols in a mapping manner of a BPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.
 11. The apparatus according to claim 9, wherein the lower order modulation symbols are quadrature phase shift keying (QPSK) symbols, the precoding matrix ${Q = {\frac{1}{\sqrt{85}}\begin{bmatrix} 8 & 4 & {- 2} & 1 \\ 4 & {- 8} & 1 & 2 \\ 2 & 1 & 8 & {- 4} \\ 1 & {- 2} & {- 4} & {- 8} \end{bmatrix}}},$ and demodulating the 4m estimated values of QPSK modulation symbols in a mapping manner of a QPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end.
 12. The apparatus according to claim 9, wherein the lower order modulation symbols are quadrature phase shift keying (QPSK) symbols, the precoding matrix ${Q = {\frac{1}{2}\begin{bmatrix} 1 & 1 & 1 & e^{j\; 0.25\;\pi} \\ 1 & 1 & {- 1} & {- e^{j\; 0.25\;\pi}} \\ 1 & {- 1} & {- 1} & e^{j\; 0.25\;\pi} \\ 1 & {- 1} & 1 & {- e^{j\; 0.25\;\pi}} \end{bmatrix}}},$ and wherein the demodulator is configured to demodulate the 4m estimated values of QPSK modulation symbols in a mapping manner of a QPSK constellation diagram, to obtain an estimated value of information bits sent by a transmit end. 